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(R)
TOP209/210
TOPSwitch Family
Three-terminal Off-line PWM Switch
Product Highlights
Cost Effective Switcher for Low Power Applications * Replaces linear power supplies * Replaces discrete switcher and 20 to 50 components - cuts cost, increases reliability * Stand-by power supplies for Green or energy efficient products such as personal computers, monitors, UPS, copiers, fax machines, etc. * Housekeeping or "keep-alive" power supply applications such as TV, appliances, industrial control and personal computers * Meets 'Blue Angel' low power stand-by specification * Controlled MOSFET turn-on reduces EMI and EMI filter costs * 80% smaller and lighter compared to linear supply * 50% smaller compared to discrete switcher Over 80% Efficiency in Flyback Topology * Built-in start-up and current limit reduce DC losses * Low capacitance 700 V MOSFET cuts AC losses * CMOS controller/gate driver consumes only 6 mW * 70% maximum duty cycle minimizes conduction losses Simplifies Design - Reduces Time to Market * Supported by reference design boards * Integrated PWM Controller and 700 V MOSFET in industry standard eight pin DIP package * Only one external capacitor needed for compensation, bypass and start-up/auto-restart functions * Easily interfaces with both opto and primary feedback System Level Fault Protection Features * Auto-restart and cycle by cycle current limiting functions handle both primary and secondary faults * On-chip thermal shutdown with hysteresis protects the entire system against overload
(R)
+
Wide-Range DC Input TOPSwitch -
D
CONTROL
C
S
PI-2043-052397
Figure 1. Typical Application.
TOPSwitch Selection Guide
ORDER PART NUMBER OUTPUT POWER RANGE PACKAGE
230 VAC or 110 VAC w/Doubler 85-265 VAC
TOP209P TOP209G TOP210PFI TOP210G
DIP-8 SMD-8 DIP-8 SMD-8
0-4 W
0-2 W
0-8 W
0-5 W
Description
The TOP209/210 implements all functions necessary for an off-line switched mode control system: high voltage N-channel power MOSFET with controlled turn-on gate driver, voltage mode PWM controller with integrated oscillator, high voltage start-up bias circuit, bandgap derived reference, bias shunt regulator/error amplifier for loop compensation and fault protection circuitry. Compared to discrete MOSFET and controller or self oscillating (RCC) switching converter solutions, a TOPSwitch integrated circuit can reduce total cost, component count, size, weight and at the same time increase efficiency and system reliability. The TOP209/210 are intended for 100/110/230 VAC off-line Power Supply applications in the 0 to 8 W (0 to 5 W universal) range.
August 1997
TOP209/210
VC CONTROL ZC SHUNT REGULATOR/ ERROR AMPLIFIER
+
5.7 V 5.7 V 4.7 V 0
DRAIN
1 INTERNAL SUPPLY
SHUTDOWN/ AUTO-RESTART
+ -
/8
POWER-UP RESET + IFB THERMAL SHUTDOWN WITH HYSTERESIS
OSCILLATOR
DMAX CLOCK SAW
VI
LIMIT
CONTROLLED TURN-ON GATE DRIVER
+
PWM COMPARATOR
S R
Q Q
LEADING EDGE BLANKING MINIMUM ON-TIME DELAY
RE
SOURCE
PI-1742-011796
Figure 2. Functional Block Diagram.
Pin Functional Description
2
DRAIN Pin: Output MOSFET drain connection. Provides internal bias current during start-up operation via an internal switched highvoltage current source. Internal current sense point. CONTROL Pin: Error amplifier and feedback current input pin for duty cycle control. Internal shunt regulator connection to provide internal bias current during normal operation. It is also used as the supply bypass and auto-restart/compensation capacitor connection point. SOURCE Pin: Control circuit common, internally connected to output MOSFET source. SOURCE (HV RTN) Pin: Output MOSFET source connection for high voltage return.
SOURCE 1 N/C 2 N/C 3 CONTROL 4
8 7 6 5
SOURCE (HV RTN) N/C N/C DRAIN
P Package (DIP-8) G Package (SMD-8)
PI--2044-040901
Figure 3. Pin Configuration.
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TOP209/210
TOPSwitch Family Functional Description
TOPSwitch is a self biased and protected linear control current-to-duty cycle converter with an open drain output. High efficiency is achieved through the use of CMOS and integration of the maximum number of functions possible. CMOS significantly reduces bias currents as compared to bipolar or discrete solutions. Integration eliminates external power resistors used for current sensing and/or supplying initial start-up bias current. During normal operation, the internal output MOSFET duty cycle linearly decreases with increasing CONTROL pin current as shown in Figure 4. To implement all the required control, bias, and protection functions, the DRAIN and CONTROL pins each perform several functions as described below. Refer to Figure 2 for a block diagram and Figure 6 for timing and voltage waveforms of the TOPSwitch integrated circuit. Control Voltage Supply CONTROL pin voltage VC is the supply or bias voltage for the controller and driver circuitry. An external bypass capacitor closely connected between the CONTROL and SOURCE pins is required to supply the gate drive current. The total amount of capacitance connected to this pin (CT) also sets the auto-restart timing as well as control loop compensation. VC is regulated in either of two modes of operation. Hysteretic regulation is used for initial start-up and overload operation. Shunt regulation is used to separate the duty cycle error signal from the control circuit supply current. During start-up, VC current is supplied from a high-voltage switched current source connected internally between the DRAIN and CONTROL pins. The current source provides sufficient current to supply the control circuitry as well as charge the total external capacitance (CT).
Auto-restart DMAX IB Slope = PWM Gain -16%/mA
Duty Cycle (%)
DMIN ICD1 2.5
6.5
IC (mA)
Figure 4. Relationship of Duty Cycle to CONTROL Pin Current.
PI-2047-060497
VC
5.7 V 4.7 V 0 VIN 0
IC Charging CT
Off
DRAIN
Switching
(a)
IC Charging CT ICD1 Discharging CT ICD2 Discharging CT
VC
5.7 V 4.7 V
8 Cycles
0
95% 5% Off
DRAIN
VIN 0
Off
Off
Switching
Switching
(b)
CT is the total external capacitance connected to the CONTROL pin
PI-1124A-060694
Figure 5. Start-up Waveforms for (a) Normal Operation and (b) Auto-restart.
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TOP209/210
TOPSwitch Family Functional Description (cont.)
The first time VC reaches the upper threshold, the high-voltage current source is turned off and the PWM modulator and output transistor are activated, as shown in Figure 5(a). During normal operation (when the output voltage is regulated) feedback control current supplies the VC supply current. The shunt regulator keeps VC at typically 5.7 V by shunting CONTROL pin feedback current exceeding the required DC supply current through the PWM error signal sense resistor RE. The low dynamic impedance of this pin (ZC) sets the gain of the error amplifier when used in a primary feedback configuration. The dynamic impedance of the CONTROL pin together with the external resistance and capacitance determines the control loop compensation of the power system. If the CONTROL pin external capacitance (CT) should discharge to the lower threshold, then the output MOSFET is turned off and the control circuit is placed in a low-current standby mode. The high-voltage current source is turned on and charges the external capacitance again. Charging current is shown with a negative polarity and discharging current is shown with a positive polarity in Figure 6. The hysteretic auto-restart comparator keeps VC within a window of typically 4.7 to 5.7 V by turning the high-voltage current source on and off as shown in Figure 5(b). The auto-restart circuit has a divide-by-8 counter which prevents the output MOSFET from turning on again until eight discharge-charge cycles have elapsed. The counter effectively limits TOPSwitch power dissipation by reducing the auto-restart duty cycle to typically 5%. Autorestart continues to cycle until output voltage regulation is again achieved. Bandgap Reference All critical TOPSwitch internal voltages are derived from a temperature-compensated bandgap reference. This reference is also used to generate a temperature-compensated current source which is trimmed to accurately set the oscillator frequency and MOSFET gate drive current. Oscillator The internal oscillator linearly charges and discharges the internal capacitance between two voltage levels to create a sawtooth waveform for the pulse width modulator. The oscillator sets the pulse width modulator/current limit latch at the beginning of each cycle. The nominal frequency of 100 kHz was chosen to minimize EMI and maximize efficiency in power supply applications. Trimming of the current reference improves oscillator frequency accuracy. Pulse Width Modulator The pulse width modulator implements a voltage-mode control loop by driving the output MOSFET with a duty cycle inversely proportional to the current flowing into the CONTROL pin. The error signal across RE is filtered by an RC network with a typical corner frequency of 7 kHz to reduce the effect of switching noise. The filtered error signal is compared with the internal oscillator sawtooth waveform to generate the duty cycle waveform. As the control current increases, the duty cycle decreases. A clock signal from the oscillator sets a latch which turns on the output MOSFET. The pulse width modulator resets the latch, turning off the output MOSFET. The maximum duty cycle is set by the symmetry of the internal oscillator. The modulator has a minimum ON-time to keep the current consumption of the TOPSwitch independent of the error signal. Note that a minimum current must be driven into the CONTROL pin before the duty cycle begins to change. Gate Driver The gate driver is designed to turn the output MOSFET on at a controlled rate to minimize common-mode EMI. The gate drive current is trimmed for improved accuracy. Error Amplifier The shunt regulator can also perform the function of an error amplifier in primary feedback applications. The shunt regulator voltage is accurately derived from the temperature compensated bandgap reference. The gain of the error amplifier is set by the CONTROL pin dynamic impedance. The CONTROL pin clamps external circuit signals to the VC voltage level. The CONTROL pin current in excess of the supply current is separated by the shunt regulator and flows through RE as the error signal. Cycle-By-Cycle Current Limit The cycle by cycle peak drain current limit circuit uses the output MOSFET ON-resistance as a sense resistor. A current limit comparator compares the output MOSFET ON-state drainsource voltage, VDS(ON), with a threshold voltage. High drain current causes VDS(ON) to exceed the threshold voltage and turns the output MOSFET off until the start of the next clock cycle. The current limit comparator threshold voltage is temperature compensated to minimize variation of the effective peak current limit due to temperature related changes in output MOSFET RDS(ON). The leading edge blanking circuit inhibits the current limit comparator for a short time after the output MOSFET is turned on. The leading edge blanking time has been set so that current spikes caused by primary-side capacitances and secondary-side rectifier reverse recovery time will not cause premature termination of the switching pulse.
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TOP209/210
VIN
VIN
DRAIN
0
VOUT
0
IOUT
0
1
2
8
1
2
8
1
VC
0
***
***
1
2
8
1
2
8
1
IC
0
***
1 2
***
1
PI-1742-011796
Figure 6. Typical Waveforms for (1) Normal Operation, (2) Auto-restart.
Shutdown/Auto-restart To minimize TOPSwitch power dissipation, the shutdown/ auto-restart circuit turns the power supply on and off at a duty cycle of typically 5% if an out of regulation condition persists. Loss of regulation interrupts the external current into the CONTROL pin. VC regulation changes from shunt mode to the hysteretic auto-restart mode described above. When the fault condition is removed, the power supply output becomes regulated, VC regulation returns to shunt mode, and normal operation of the power supply resumes. Hysteretic Overtemperature Protection Temperature protection is provided by a precision analog circuit that turns the output MOSFET off when the junction temperature exceeds the thermal shutdown temperature
(typically 145 C). When the junction temperature cools past the hysteresis temperature, normal operation resumes. VC is regulated in hysteretic mode while the power supply is turned off. High-voltage Bias Current Source This current source biases TOPSwitch from the DRAIN pin and charges the CONTROL pin external capacitance (CT) during start-up or hysteretic operation. The current source is switched on and off with an effective duty cycle of approximately 35%. This duty cycle is determined by the ratio of CONTROL pin charge (IC) and discharge currents (ICD1 and ICD2). This current source is turned off during normal operation when the output MOSFET is switching.
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TOP209/210 General Circuit Description
Figure 7 shows a low-cost, DC input, flyback switching power supply using the TOP210 integrated circuit. This 5 V, 4 W power supply operates from a DC voltage derived from rectified and filtered AC mains voltage of 85 to 265 VAC. The 5 V output is indirectly sensed via the primary bias winding. The output voltage is determined by the TOPSwitch CONTROL pin shunt regulator voltage (VC), the voltage drops of rectifiers D2 and D3, and the turns ratio between the bias winding and output winding of T1. Other output voltages are also possible by adjusting the transformer turns ratios. The high voltage DC bus is applied to the primary winding of T1. Capacitor C1 filters the high voltage supply, and is only necessary if the connections between the high voltage DC supply and the TOP210 are long. The other side of the transformer primary is driven by the integrated high-voltage MOSFET within the TOP210. D1 and VR1 clamp the voltage spike caused by transformer leakage inductance to a safe value and reduce ringing at the DRAIN of U1. The power secondary winding is rectified and filtered by D2, C2, L1, and C3 to create the 5V output voltage. The bias winding is rectified and filtered by D3, R1 and C5 to create a bias voltage to the TOP210. C5 also filters internal MOSFET gate drive charge current spikes on the CONTROL pin, determines the auto-restart frequency, and together with R1, compensates the control loop.
1
D2 1N5822 8
L1 3.3 H +5 V
+
VR1 BZY97C120 120 V 5 D1 UF4005 2 4
C2 330 F 10 V
C3 100 F 10 V RTN
D3 1N4148
DC INPUT
C1 10 nF 400 V T1
D
CONTROL
3
R1 15
TRD1
C
2
TOPSwitch
S
U1 TOP210
C5 47 F 10 V
-
CIRCUIT PERFORMANCE: Line Regulation - -1.5% (104-370 VDC) Load Regulation - -5% (10-100%) Ripple Voltage -25 mV
PI-2045-041798
Figure 7. Schematic Diagram of a Minimum Parts Count 5 V, 4 W Bias Supply Using the TOP210.
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TOP209/210
1 + BR1 DFO6M RA 470 k JP1* JUMPER C1 10 F 200 V T1 T1RD2
VR1 BZY97-C200
D1 UF4005 2
D2 MBR360 8 C2 330 F 16 V 3 D3 1N4148 5
L1 3 H C3 120 F 16 V R2 330 1W
12 V
RB 470 k
C9 10 F 200 V
D
TOPSwitch
CONTROL
C
R1 6.8
RTN CIRCUIT PERFORMANCE: Line Regulation - -1% (85-132 VAC) or (170-265 VAC) Load Regulation - -5% (10-100%) Ripple Voltage - 50 mV Meets CISPR-22 Class B
L2 12 mH min. 0.2A
S
U1 TOP210
C5 47 F 10 V
F1 2A
L N J1
C6 47nF 250VAC X2
4
* JPI INSTALLED FOR 110 VAC INPUT JPI OPEN FOR 220 VAC INPUT
C7 1nF 250 VAC Y1
PI-2046-052397
Figure 8. Schematic Diagram of a 12 V, 8 W 110/220 VAC Input Power Supply Using the TOP210.
The circuit shown in Figure 8 produces a 12 V, 8 W power supply that operates from 85 to 132 VAC or 170 to 264 VAC input voltage. The 12 V output voltage is determined by the TOPSwitch CONTROL pin shunt regulator voltage, the voltage drops of D2 and D3, and the turns ratio between the bias and output windings of T1. Other output voltages are also possible by adjusting the transformer turns ratios. R1 and C5 provide filtering of the bias winding to improve line and load regulation. AC power is rectified and filtered by BR1, C1 and C9 to create the high voltage DC bus applied to the primary winding of T1. The other side of the transformer primary is driven by the integrated high-voltage MOSFET within the TOP210. JP1 is a jumper used to select 110 VAC or 220 VAC operation. Installing JP1 selects 110 VAC operation. Leaving JP1 open selects 220 VAC operation. RA and RB, which equalize voltage across
C1 and C9, are necessary only when JP1 is not installed. D1 and VR1 clamp the leading-edge voltage spike caused by transformer leakage inductance to a safe value and reduce ringing. The power secondary winding is rectified and filtered by D2, C2, L1, and C3 to create the 12 V output voltage. R2 provides a preload on the 12 V output to improve load regulation at light loads. The bias winding is rectified and filtered by D3, R1, and C5 to create a bias voltage to the TOP210. L2 and Y1-capacitor C7 attenuate common-mode emission currents caused by highvoltage switching waveforms on the DRAIN side of the primary winding and the primary to secondary capacitance. L2 and C6 attenuate differential-mode emission currents caused by the fundamental and harmonics of the trapezoidal primary current waveform. C5 filters internal MOSFET gate drive charge current spikes on the CONTROL pin, determines the autorestart frequency, and together with R1, compensates the control loop.
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TOP209/210 Key Application Considerations
Use a Kelvin connection to the SOURCE pin for the CONTROL pin bypass capacitor as shown in Figure 9. Minimize peak voltage and ringing on the DRAIN voltage at turn-off. Use a Zener or TVS Zener diode to clamp the DRAIN voltage. Under some conditions, externally provided bias or supply current driven into the CONTROL pin can hold the TOPSwitch in one of the 8 auto-restart cycles indefinitely and prevent starting. Shorting the CONTROL pin to the SOURCE pin will reset the TOPSwitch. To avoid this problem when doing bench evaluations, it is recommended that the VC power supply be turned on before the DRAIN voltage is applied. CONTROL pin currents during auto-restart operation are much lower at low input voltages (< 20 V) which increases the autorestart cycle period (see the IC vs. Drain Voltage Characteristic curve). Short interruptions of AC power may cause TOPSwitch to enter the 8-count auto-restart cycle before starting again. This is because the input energy storage capacitors are not completely discharged and the CONTROL pin capacitance has not discharged below the internal power-up reset voltage (VC(RESET)). In some cases, minimum loading may be necessary to keep a lightly loaded or unloaded output voltage within the desired range due to the minimum ON-time. For additional applications information regarding the TOPSwitch family, refer to AN-14 in the 1996-97 Data Book and Design Guide or on our Web site.
TOP210 PFI SOURCE
Bias/Feedback Return Bias/Feedback Input
SOURCE
High Voltage Return
CONTROL
Bypass Capacitor
DRAIN
2
Figure 9. Recommended PC Layout for the TOP209/210.
TOP VIEW
PI-1744-011796
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TOP209/210
ABSOLUTE MAXIMUM RATINGS(1)
DRAIN Voltage ........................................... - 0.3 to 700 V CONTROL Voltage ..................................... - 0.3 V to 9 V CONTROL Current ............................................... 100 mA Storage Temperature ..................................... -65 to 150 C Operating Junction Temperature(2) ................ -40 to 150 C Lead Temperature(3) ................................................ 260 C Thermal Impedance (JA) ................................... 100 C/W Thermal Impedance (JC) ..................................... 40 C/W 2. Normally limited by internal circuitry. 3. 1/16" from case for 5 seconds.
1. Unless noted, all voltages referenced to SOURCE, TA = 25 C.
Conditions Parameter Symbol
(Unless Otherwise Specified) See Figure 12 SOURCE = 0 V TJ = -40 to 125 C
Min
Typ
Max
Units
CONTROL FUNCTIONS Output Frequency Maximum Duty Cycle Minimum Duty Cycle PWM Gain PWM Gain Temperature Drift External Bias Current Dynamic Impedance
Dynamic Impedance
IB ZC fOSC DMAX DMIN IC = 4 mA, TJ = 25 C TOP209 TOP210 55 90 64 0.5 1.0 -11 70 100 67 1.5 1.8 -16 85 110 70 2.5 3.0 -21 %/mA kHz
IC = ICD1+ 0.5 mA, See Figure 10 IC = 10 mA See Figure 10 TOP209 TOP210
%
%
IC = 4 mA, TJ = 25 C See Figure 4 See Note A
-0.05
%/mA/C
See Figure 4 IC = 4 mA, TJ = 25 C See Figure 11
1.5
2.5
4
mA
10
15
22
Temperature Drift SHUTDOWN/AUTO-RESTART CONTROL Pin Charging Current Charging Current Temperature Drift Auto-restart Threshold Voltage VC(AR)
IC TJ = 25 C VC = 0 V VC = 5 V -2.4 -2
0.18
%/C
-1.9 -1.5 0.4
-1.2 mA -0.8 %/C
See Note A
S1 open
5.7
V
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TOP209/210
Conditions Parameter Symbol
(Unless Otherwise Specified) See Figure 12 SOURCE = 0 V TJ = -40 to 125 C
Min
Typ
Max
Units
SHUTDOWN/AUTO-RESTART (cont.) UV Lockout Threshold Voltage Auto-restart Hysteresis Voltage Auto-restart Duty Cycle Auto-restart Frequency CIRCUIT PROTECTION Self-protection Current Limit Leading Edge Blanking Time Current Limit Delay Thermal Shutdown Temperature
ILIMIT tLEB tILD di/dt = 40 mA/s, TJ = 25 C IC = 4 mA IC = 4 mA IC = 4 mA TOP209 TOP210 0.150 0.230 150 0.230 0.300 ns A S1 open 4.4 4.7 5.0 V
S1 open
0.6
1.0
V
S1 open
5
9
%
S1 open
1.2
Hz
100
ns C C
125
145
2
Thermal Shutdown Hysteresis Power-up Reset Threshold Voltage
VC(RESET) S2 open 2.0
30
3.3
4.2
V
10
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TOP209/210
Conditions Parameter Symbol
(Unless Otherwise Specified) See Figure 12 SOURCE = 0 V TJ = -40 to 125 C
Min
Typ
Max
Units
OUTPUT ON-State Resistance OFF-State Current Breakdown Voltage Rise Time Fall Time DRAIN Supply Voltage SUPPLY Shunt Regulator Voltage Shunt Regulator Temperature Drift
ICD1 ICD2 Output MOSFET Enabled 0.6 VC(SHUNT) IC = 4 mA 5.5 5.8 50 6.1 V RDS(ON) IDSS BVDSS tR tF ID = 25 mA TJ = 25 C TJ = 100 C 31.2 51.4 36.0 59.4 250 A
See Note B VDS = 560 V, TA = 125 C See Note B, ID = 100 A, TA = 25 C Measured in a Typical Flyback Converter Application 700
V
100
ns
50
ns
See Note C
36
V
ppm/C
CONTROL Supply/ Discharge Current
1.2
1.6 mA
Output MOSFET Disabled
0.5
0.8
1.1
NOTES: A. For specifications with negative values, a negative temperature coefficient corresponds to an increase in magnitude with increasing temperature, and a positive temperature coefficient corresponds to a decrease in magnitude with increasing temperature. B. The breakdown & leakage measurements can be accomplished by using the TOPSwitch auto-restart feature. The divide-by-8 counter in the auto-restart circuitry disables the output MOSFET from switching in 7 out of 8 cycles. To place the TOPSwitch in one of these cycles, the following procedure can be carried out using the modified circuit of Figure 12:
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TOP209/210
NOTES: (continued) i. The 470 5 W load resistor at the DRAIN pin should be shorted. S1 & S2 should stay closed. ii. The 40 V output supply should be replaced with a curve tracer capable of forcing 700 V. iii. The curve tracer should initially be set at 0 V. The 0-50 V variable supply should be adjusted through a voltage sequence of 0 V, 6.5 V, 4.2 V, and 6.5 V. iv. The breakdown and the leakage measurements can now be taken with the curve tracer. The maximum voltage from the curve tracer must be limited to 700 V under all conditions. C. It is possible to start up and operate TOPSwitch at DRAIN voltages well below 36 V. However, the CONTROL pin charging current is reduced, which affects start-up time and auto-restart frequency and duty cycle. Refer to the characteristic graph on CONTROL pin charge current (IC) vs. DRAIN voltage for low voltage operation characteristics.
TYPICAL CONTROL PIN I-V CHARACTERISTIC
CONTROL Pin Current (mA)
PI-1745-011796
120 100 80 60 40 20 0 0
PI-2048-050798
t2 t1
HV DRAIN VOLTAGE
90%
90%
t D= 1 t2
10%
Dynamic 1 = Impedance Slope
0V
2
4
6
8
10
CONTROL Pin Voltage (V)
Figure 11. TOPSwitch CONTROL Pin I-V Characteristic.
Figure 10. TOPSwitch Duty Cycle Measurement.
2
D C
470 5W 470 S1 S S 0.1 F
S2
40 V 47 F 0-50 V
NOTE: This test circuit is not applicable for current limit or output characteristic measurements.
PI-1733-122095
Figure 12. TOPSwitch General Test Circuit.
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TOP209/210
BENCH TEST PRECAUTIONS FOR EVALUATION OF ELECTRICAL CHARACTERISTICS
The following precautions should be followed when testing TOPSwitch by itself outside a power supply. The schematic shown in Figure 12 is suggested for laboratory testing of TOPSwitch. When the DRAIN supply is turned on, the part will be in the auto-restart mode. The CONTROL pin voltage will be oscillating at a low frequency from 4.7 to 5.7 V and the DRAIN is turned on every eighth cycle of the CONTROL pin oscillation. If the CONTROL pin power supply is turned on while in this auto-restart mode, there is only a 12.5% chance that the CONTROL pin oscillation will be in the correct state (DRAIN active state) so that the continuous DRAIN voltage waveform may be observed. It is recommended that the VC power supply be turned on first and the DRAIN power supply second if continuous DRAIN voltage waveforms are to be observed. The 12.5% chance of being in the correct state is due to the 8:1 counter.
Typical Performance Characteristics
BREAKDOWN vs. TEMPERATURE
PI-176B-051391
FREQUENCY vs. TEMPERATURE
PI-1123A-060794
1.1
1.2
1.0 0.8 0.6 0.4 0.2
Breakdown Voltage (V) (Normalized to 25 C)
1.0
0.9 -50 -25 0 25 50 75 100 125 150
Output Frequency (Normalized to 25 C)
0 -50 -25 0 25 50 75 100 125 150
Junction Temperature (C)
Junction Temperature (C)
CURRENT LIMIT vs. TEMPERATURE
PI-1125-041494
IC vs. DRAIN VOLTAGE
VC = 5 V
PI-2074-070897
1.2
1.0 0.8 0.6 0.4 0.2
2
CONTROL Pin Charging Current (mA)
Current Limit (Normalized to 25 C)
1.6
1.2
0.8
0.4
0 -50 -25 0 25 50 75 100 125 150
0 0 20 40 60 80 100
Junction Temperature (C)
DRAIN Voltage (V)
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TOP209/210 Typical Performance Characteristics (cont.)
OUTPUT CHARACTERISTIC
PI-1734-011596
COSS vs. DRAIN VOLTAGE
PI-1730-121995
300 250
TCASE=25 C TCASE=100 C
100
200 150 100 50 0 0 2 4 6 8 10
DRAIN Capacitance (pF)
Drain Current (mA)
10
1 0 200 400 600
DRAIN Voltage (V)
DRAIN Voltage (V)
DRAIN CAPACITANCE POWER
PI-1731-121995
50
40
Power (mW)
30
20
10
2
0 0 200 400 600
DRAIN Voltage (V)
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DIP-8
DIM A B C G H J1 J2 K L M N P Q inches 0.370-0.385 0.245-0.255 0.125-0.135 0.015-0.040 0.120-0.135 0.060 (NOM) 0.014-0.022 0.010-0.012 0.090-0.110 0.030 (MIN) 0.300-0.320 0.300-0.390 0.300 BSC mm
8
D S .004 (.10)
5
9.40-9.78 6.22-6.48 3.18-3.43 0.38-1.02 3.05-3.43 1.52 (NOM) 0.36-0.56 0.25-0.30 2.29-2.79 0.76 (MIN) 7.62-8.13 7.62-9.91 7.62 BSC
-E-
B
1
4
A M J1
-DN
Notes: 1. Package dimensions conform to JEDEC specification MS-001-AB for standard dual in-line (DIP) package .300 inch row spacing (PLASTIC) 8 leads (issue B, 7/85).. 2. Controlling dimensions are inches. 3. Dimensions shown do not include mold flash or other protrusions. Mold flash or protrusions shall not exceed .006 (.15) on any side. 4. D, E and F are reference datums on the molded body.
C
-FG J2 L H K Q P
P08A
PI-2076-041101
SMD-8
D S .004 (.10)
Heat Sink is 2 oz. Copper As Big As Possible
5
DIM A B C G H J1 J2 J3 J4 K L M P
inches 0.370-0.385 0.245-0.255 0.125-0.135 0.004-0.012 0.036-0.044 0.060 (NOM) 0.048-0.053 0.032-0.037 0.007-0.011 0.010-0.012 0.100 BSC 0.030 (MIN) 0.372-0.388 0-8
mm 9.40-9.78 6.22-6.48 3.18-3.43 0.10-0.30 0.91-1.12 1.52 (NOM) 1.22-1.35 0.81-0.94 0.18-0.28 0.25-0.30 2.54 BSC 0.76 (MIN) 9.45-9.86 0-8
-E-
8
E S .010 (.25)
B
P
.420 .046 .060 .060 .046
1
4
Pin 1 .086 .186
.080
L
A M J1
-D-
.286
Solder Pad Dimensions
C
K
-F.004 (.10) J3 J4 J2 .010 (.25) M A S G H
G08A
Notes: 1. Package dimensions conform to JEDEC specification MS-001-AB (issue B, 7/85) except for lead shape and size. 2. Controlling dimensions are inches. 3. Dimensions shown do not include mold flash or other protrusions. Mold flash or protrusions shall not exceed .006 (.15) on any side. 4. D, E and F are reference datums on the molded body.
PI-2077-042601
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TOP209/210
For the latest updates, visit our Web site: www.powerint.com Power Integrations reserves the right to make changes to its products at any time to improve reliability or manufacturability. Power Integrations does not assume any liability arising from the use of any device or circuit described herein, nor does it convey any license under its patent rights or the rights of others. The PI Logo, TOPSwitch, TinySwitch and EcoSmart are registered trademarks of Power Integrations, Inc. (c)Copyright 2001, Power Integrations, Inc.
WORLD HEADQUARTERS AMERICAS Power Integrations, Inc. 5245 Hellyer Avenue San Jose, CA 95138 USA Main: +1 408-414-9200 Customer Service: Phone: +1 408-414-9665 Fax: +1 408-414-9765 e-mail: usasales@powerint.com KOREA Power Integrations International Holdings, Inc. Rm# 402, Handuk Building 649-4 Yeoksam-Dong, Kangnam-Gu, Seoul, Korea Phone: +82-2-568-7520 Fax: +82-2-568-7474 e-mail: koreasales@powerint.com EUROPE & AFRICA Power Integrations (Europe) Ltd. Centennial Court Easthampstead Road Bracknell Berkshire, RG12 1YQ United Kingdom Phone: +44-1344-462-300 Fax: +44-1344-311-732 e-mail: eurosales@powerint.com JAPAN Power Integrations, K.K. Keihin-Tatemono 1st Bldg. 12-20 Shin-Yokohama 2-Chome Kohoku-ku, Yokohama-shi Kanagawa 222-0033, Japan Phone: +81-45-471-1021 Fax: +81-45-471-3717 e-mail: japansales@powerint.com TAIWAN Power Integrations International Holdings, Inc. 17F-3, No. 510 Chung Hsiao E. Rd., Sec. 5, Taipei, Taiwan 110, R.O.C. Phone: +886-2-2727-1221 Fax: +886-2-2727-1223 e-mail: taiwansales@powerint.com INDIA (Technical Support) Innovatech #1, 8th Main Road Vasanthnagar Bangalore, India 560052 Phone: +91-80-226-6023 Fax: +91-80-228-9727 e-mail: indiasales@powerint.com CHINA Power Integrations International Holdings, Inc. Rm# 1705, Bao Hua Bldg. 1016 Hua Qiang Bei Lu Shenzhen, Guangdong 518031 China Phone: +86-755-367-5143 Fax: +86-755-377-9610 e-mail: chinasales@powerint.com APPLICATIONS HOTLINE World Wide +1-408-414-9660 APPLICATIONS FAX World Wide +1-408-414-9760
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